FUJITSU SEMICONDUCTOR
DATA SHEET
DS04-27231-3E
ASSP For Power Management Applications
(General Purpose DC/DC Converter)
2-ch DC/DC Converter IC
with Overcurrent Protection
MB39A104
■ DESCRIPTION
The MB39A104 is a 2-channel DC/DC converter IC using pulse width modulation (PWM), incorporating an
overcurrent protection circuit (requiring no current sense resistor). This IC is ideal for down conversion.
Operating at high frequency reduces the value of coil.
This is ideal for built-in power supply such as LCD monitors and ADSL.
This product is covered by US Patent Number 6,147,477.
■ FEATURES
• Built-in timer-latch overcurrent protection circuit (requiring no current sense resistor)
• Power supply voltage range : 7 V to 19 V
• Reference voltage : 5.0 V ± 1 %
• Error amplifier threshold voltage : 1.24 V ± 1 %
• High-frequency operation capability : 1.5 MHz (Max)
• Built-in standby function: 0 µA (Typ)
• Built-in soft-start circuit independent of loads
• Built-in totem-pole type output for Pch MOS FET
■ PACKAGE
24-pin plastic SSOP
(FPT-24P-M03)
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MB39A104
■ PIN DESCRIPTION
Pin No.
Symbol
VCCO
VH
I/O
Descriptions
1
2
3
4
Output circuit power supply terminal (Connect to same potential as VCC pin.)
Power supply terminal for FET drive circuit (VH = VCC − 5 V)
External Pch MOS FET gate drive terminal
O
O
I
OUT1
VS1
Overcurrent protection circuit input terminal
Overcurrent protection circuit detection resistor connection terminal. Set
overcurrent detection reference voltage depending on external resistor and
internal current resource (110 µA at RT = 24 kΩ)
5
ILIM1
I
I
PWM comparator block (PWM) input terminal. Compares the lowest voltage
among FB1 and DTC terminals with triangular wave and controls output.
6
7
DTC1
VCC
Power supply terminal for reference power supply and control circuit
(Connect to same potential as the VCCO terminal)
8
CSCP
FB1
Timer-latch short-circuit protection capacitor connection terminal
Error amplifier (Error Amp 1) output terminal
9
O
I
10
11
12
13
14
15
16
17
−INE1
CS1
RT
Error amplifier (Error Amp 1) inverted input terminal
Soft-start capacitor connection terminal
Triangular wave oscillation frequency setting resistor connection terminal
Triangular wave oscillation frequency setting capacitor connection terminal
Soft-start capacitor connection terminal
CT
CS2
−INE2
FB2
I
Error amplifier (Error Amp 2) inverted input terminal
Error amplifier (Error Amp 2) output terminal
O
O
VREF
Reference voltage output terminal
Output circuit ground terminal (Connect to same potential as GNDO
terminal.)
18
19
GND
PWM comparator block (PWM) input terminal. Compares the lowest voltage
among FB2 and DTC terminals with triangular wave and controls output.
DTC2
I
I
Overcurrent protection circit detection resistor connection terminal. Set
overcurrent detection reference voltage depending on external resistor and
internal current resource (110 µA at RT = 24 kΩ)
20
ILIM2
21
22
23
VS2
I
Overcurrent protection circuit input terminal
OUT2
GNDO
O
External Pch MOS FET gate drive terminal
Output circuit ground terminal (Connect to same potential as GND terminal.)
Power supply control terminal. Setting the CTL terminal at “L” level places IC
in the standby mode.
24
CTL
I
3
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MB39A104
■ BLOCK DIAGRAM
−INE1 10
1
3
VCCO
OUT1
CH1
L priority
VREF
1.24 V
Error
PWM
Comp.1
Amp1
10 µA
CS1 11
−
+
+
Drive1
Pch
+
+
−
L priority
FB1
9
IO = 200 mA
at VCCO = 12 V
−
+
4
5
VS1
Current
Protection
Logic
ILIM1
DTC1
6
−INE2 15
CH2
L priority
VREF
1.24 V
Error
PWM
Comp.2
Amp2
10 µA
CS2 14
−
+
+
+
+
Drive2
Pch
22 OUT2
−
L priority
FB2 16
IO = 200 mA
at VCCO = 12 V
DTC2 19
−
+
21 VS2
Current
Protection
Logic
H priority
H: at SCP
20 ILIM2
SCP
Comp.
+
+
−
(3.1 V)
H: at OCP
VH
VCC − 5 V
2
VH
Bias
Voltage
SCP
Logic
CSCP
8
23 GNDO
2.5 V
1.5 V
Error Amp Power Supply
Error Amp Reference
UVLO
7
VCC
H:UVLO
release
1.24 V
Power
bias
24 CTL
OSC
ON/OFF
CTL
VREF
VR1
Accuracy
±1%
5.0 V
12 13
RT CT
17
18
VREF
GND
4
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MB39A104
■ ABSOLUTE MAXIMUM RATINGS
Rating
Parameter
Symbol
Condition
Unit
Max
Min
Power supply voltage
Output current
VCC
IO
VCC, VCCO terminal
OUT1, OUT2 terminal
Duty ≤ 5% (t = 1/fOSC×Duty)
Ta ≤ +25 °C
20
60
V
mA
mA
mW
°C
Output peak current
Power dissipation
Storage temperature
IOP
700
740*
+125
PD
TSTG
−55
* : The packages are mounted on the epoxy board (10 cm × 10 cm).
WARNING: Semiconductor devices can be permanently damaged by application of stress (voltage, current,
temperature, etc.) in excess of absolute maximum ratings. Do not exceed these ratings.
■ RECOMMENDED OPERATING CONDITIONS
Value
Parameter
Symbol
Condition
Unit
Min
7
Typ
Max
19
Power supply voltage
VCC
IREF
IVH
VCC, VCCO terminal
VREF terminal
12
V
mA
mA
V
Reference voltage output current
VH output current
−1
0
0
VH terminal
30
VINE
VDTC
VCTL
IO
−INE1, −INE2 terminal
DTC1, DTC2 terminal
CTL terminal
0
VCC − 0.9
VCC − 0.9
19
Input voltage
0
V
Control input voltage
Output current
0
V
OUT1, OUT2 terminal
Duty ≤ 5% (t = 1/fOSC×Duty)
−45
−450
+45
+450
mA
mA
Output Peak current
IOP
Overcurrent detection
by ON resistance of FET
100
500
1000
kHz
Oscillation frequency
fOSC
*
100
39
500
100
24
1500
560
130
1.0
kHz
pF
Timing capacitor
CT
RT
Timing resistor
11
kΩ
µF
µF
µF
VH terminal capacitor
Soft-start capacitor
Short-circuit detection capacitor
CVH
CS
VH terminal
0.1
0.1
0.1
CS1, CS2 terminal
CSCP terminal
1.0
CSCP
1.0
Reference voltage output
capacitor
CREF
Ta
VREF terminal
0.1
1.0
µF
°C
Operating ambient temperature
−30
+25
+85
* : See“ ■ SETTING THE TRIANGULAR OSCILLATION FREQUENCY”.
WARNING: The recommended operating conditions are required in order to ensure the normal operation of the
semiconductor device. All of the device’s electrical characteristics are warranted when the device is
operated within these ranges.
Always use semiconductor devices within their recommended operating condition ranges. Operation
outside these ranges may adversely affect reliability and could result in device failure.
No warranty is made with respect to uses, operating conditions, or combinations not represented on
the data sheet. Users considering application outside the listed conditions are advised to contact their
FUJITSU representatives beforehand.
5
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MB39A104
■ ELECTRICAL CHARACTERISTICS
(VCC = VCCO = 12 V, VREF = 0 mA, Ta = +25 °C)
Value
Symbol
Parameter
Output voltage
Pin No
Conditions
Ta = +25 °C
Unit
Min
Typ
Max
VREF
17
4.95 5.00 5.05
V
Output voltage
temperature
variation
∆VREF/
VREF
17
Ta = 0 °C to +85 °C
0.5*
%
Input stability
Load stability
Line
17
17
VCC = 7 V to 19 V
3
1
10
10
mV
mV
Load
VREF = 0 mA to −1 mA
Short-cuircuit
output current
IOS
VTLH
VTHL
VH
17
17
17
17
8
VREF = 1 V
VREF =
−50
2.6
2.4
−25
2.8
−12
3.0
2.8
mA
V
Threshold
voltage
VREF =
2.6
V
Hysteresis
width
0.2 *
V
Threshold
voltage
VTH
0.68 0.73 0.78
V
Input source
current
ICSCP
VRST
8
−1.4 −1.0 −0.6
µA
Reset voltage
17
VREF =
2.4
2.6
2.8
V
Threshold
voltage
VTH
8
2.8
3.1
3.4
V
Oscillation
frequency
fOSC
13
13
CT = 100 pF, RT = 24 kΩ 450
Ta = 0 °C to +85 °C
500
1*
550 kHz
Frequency
temperature
variation
∆fOSC/
fOSC
%
Charge current
ICS
11, 14
CS1 = CS2 = 0 V
−14
−10
−6
µA
Threshold
voltage
VTH
IB
9, 16
10, 15
9, 16
FB1 = FB2 = 2 V
−INE1 = −INE2 = 0 V
DC
1.227 1.240 1.253
−120 −30
100*
V
Input bias
current
nA
dB
Voltage gain
AV
(Continued)
6
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MB39A104
(Continued)
(VCC = VCCO = 12 V, VREF = 0 mA, Ta = +25 °C)
Value
Parameter
Symbol
Pin No.
Conditions
AV = 0 dB
Unit
Min Typ Max
Frequency
bandwidth
BW
9, 16
1.6*
MHz
VOH
9, 16
9, 16
4.7
4.9
40
V
Output voltage
VOL
200 mV
Output source
current
ISOURCE
ISINK
9, 16
9, 16
6, 19
FB1 = FB2 = 2 V
FB1 = FB2 = 2 V
Duty cycle = 0 %
−2
−1
mA
µA
V
Output sink current
150 200
VT0
1.4
1.5
2.5
Threshold voltage
VT100
IDTC
ILIM
6, 19
6, 19
5, 20
Duty cycle = Dtr
2.6
V
Input current
DTC1 = DTC2 = 0.4 V
−2.0 −0.6
µA
ILIM terminal input
current
RT = 24 kΩ, CT = 100 pF 99
110 121 µA
Offset voltage
Output voltage
VIO
5, 20
1 *
mV
VCC− VCC− VCC−
VCC = VCCO = 7 V to 19 V
VH = 0 mA to 30 mA
VH
ISOURCE
ISINK
2
V
5.5
5.0
4.5
OUT1 to OUT4 = 7 V,
Duty ≤ 5 %
(t = 1/fOSC×Duty)
Output source
current
3, 22
3, 22
−300
mA
mA
OUT1 to OUT4 = 12 V,
Duty ≤ 5 %
(t = 1/fOSC×Duty)
Output sink current
350
ROH
ROL
VIH
3, 22
3, 22
24
OUT1 = OUT2 = −45 mA
OUT1 = OUT2 = 45 mA
IC Active mode
8.0 12.0
Ω
Ω
V
V
Output ON
resistor
6.5
50
9.7
19
2
0
CTL input voltage
VIL
24
IC Standby mode
CTL = 5 V
0.8
ICTLH
24
100 µA
Input current
ICTLL
24
CTL = 0 V
CTL = 0 V
1
µA
µA
Standby current
ICCS
1, 17
0
10
Power supply
current
ICC
1, 17
CTL = 5 V
4.0
6.0 mA
*: Standard design value.
7
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MB39A104
■ TYPICAL CHARACTERISTICS
Power Supply Current vs. Power Supply Voltage
Reference Voltage vs. Power Supply Voltage
10
10
Ta = +25 °C
Ta = +25 °C
CTL = 5 V
CTL = 5 V
VREF = 0 mA
8
8
6
4
2
0
6
4
2
0
0
5
10
15
20
0
5
10
15
20
Power supply voltage VCC (V)
Power supply voltage VCC (V)
Reference Voltage vs. Ambient Temperature
Reference Voltage vs. Ambient Temperature
2.0
10
VCC = 12 V
Ta = +25 °C
CTL = 5 V
1.5
1.0
VCC = 12 V
VREF = 0 mA
CTL = 5 V
8
6
4
2
0
0.5
0.0
−0.5
−1.0
−1.5
−2.0
−40
−20
0
20
40
60
80
100
0
5
10
15
20
25
30
35
Ambient temperature Ta (°C)
Ambient temperature Ta (°C)
CTL terminal Current vs. CTL terminal Voltage
500
400
300
200
100
0
10
9
8
7
6
5
4
3
2
1
0
Ta = +25 °C
VCC = 12 V
VREF = 0 mA
VREF
ICTL
0
5
10
15
20
CTL terminal voltage VCTL (V)
(Continued)
8
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MB39A104
Triangular Wave Oscillation Frequency
vs. Timing Capacitor
Triangular Wave Oscillation Frequency
vs. Timing Resistor
10000
10000
Ta = +25 °C
Ta = +25 °C
VCC = 12 V
CTL = 5 V
VCC = 12 V
CTL = 5 V
1000
1000
100
10
RT = 11 kΩ
CT = 39 pF
RT = 24 kΩ
100
CT = 560 pF
RT = 130 kΩ
RT = 68 kΩ
CT = 220 pF
CT = 100 pF
10
10
100
1000
10000
1
10
100
1000
Timing resistor RT (kΩ)
Timing capacitor CT (pF)
Triangular Wave Upper and Lower Limit Voltage
vs. Ambient Temperature
Triangular Wave Upper and Lower Limit Voltage
vs. Triangular Wave Oscillation Frequency
3.2
3.2
VCC = 12 V
Ta = +25 °C
3.0
3.0
2.8
2.6
2.4
2.2
2.0
1.8
1.6
1.4
1.2
CTL = 5 V
VCC = 12 V
CTL = 5 V
RT = 24 kΩ
2.8
CT = 100 pF
RT = 47 kΩ
Upper
Upper
2.6
2.4
2.2
2.0
1.8
Lower
1.6
Lower
1.4
1.2
−40 −20
0
20
40
60
80
100
0
200 400 600 800 1000 1200 1400 1600
Ambient temperature Ta ( °C)
Triangular wave oscillation frequency fOSC (kHz)
Triangular Wave Oscillation Frequency
vs. Ambient Temperature
Triangular Wave Oscillation Frequency
vs. Power supply voltage
560
560
VCC = 12 V
CTL = 5 V
Ta = +25 °C
CTL = 5 V
540
520
500
480
460
440
RT = 24 kΩ
CT = 100 pF
540
520
500
480
460
440
RT = 24 kΩ
CT = 100 pF
−40 −20
0
20
40
60
80
100
0
5
10
15
20
Ambient temperature Ta ( °C)
Power supply voltage VCC (V)
(Continued)
9
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MB39A104
(Continued)
Error Amplifier, Gain, Phase vs. Frequency
Ta = +25 °C
VCC = 12 V
40
30
180
240 kΩ
AV
ϕ
20
90
10 kΩ
(15)
10
1 µF
10
+
−
0
0
2.4 kΩ
IN
9
+
+
11
(14)
−10
−20
−30
−40
(16)
10 kΩ
OUT
Error Amp1
(Error Amp2)
−90
−180
1.24 V
100
1 k
10 k 100 k
1 M
10 M
Frequency f (Hz)
Power Dissipation vs. Ambient Temperature
1000
800
740
600
400
200
0
−40
−20
0
20
40
60
80
100
Ambient temperature Ta ( °C)
10
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MB39A104
■ FUNCTIONS
1. DC/DC Converter Functions
(1) Reference voltage block (REF)
The reference voltage circuit generates a temperature-compensated reference voltage (5.0 V Typ) from the
voltage supplied from the power supply terminal (pin 7). The voltage is used as the reference voltage for the
IC’s internal circuitry.
The reference voltage can supply a load current of up to 1 mA to an external device through the VREF terminal
(pin 17).
(2) Triangular-wave oscillator block (OSC)
The triangular wave oscillator incorporates a timing capacitor and a timing resistor connected respectively to
the CT terminal (pin 13) and RT terminal (pin 12) to generate triangular oscillation waveform amplitude of 1.5 V
to 2.5 V.
The triangular waveforms are input to the PWM comparator in the IC.
(3) Error amplifier block (Error Amp1, Error Amp2)
The error amplifier detects the DC/DC converter output voltage and outputs PWM control signals. In addition,
an arbitrary loop gain can be set by connecting a feedback resistor and capacitor from the output terminal to
inverted input terminal of the error amplifier, enabling stable phase compensation to the system.
Also, it is possible to prevent rush current at power supply start-up by connecting a soft-start capacitor with the
CS1 terminal (pin 11) and CS2 terminal (pin 14) which are the non-inverted input terminal for Error Amp. The
use of Error Amp for soft-start detection makes it possible for a system to operate on a fixed soft-start time that
is independent of the output load on the DC/DC converter.
(4) PWM comparator block (PWM Comp.)
The PWM comparator is a voltage-to-pulse width modulator that controls the output duty depending on the input/
output voltage.
The comparator keeps output transistor on while the error amplifier output voltage remain higher than the
triangular wave voltage.
(5) Output block
The output block is in the totem pole configuration, capable of driving an external P-channel MOS FET.
(6) Bias voltage block (VH)
This bias voltage circuit outputs VCC − 5 V(Typ) as minimum potential of the output circuit. In standby mode, this
circuit outputs the potential equal to VCC.
11
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MB39A104
2. Control Function
When CTL terminal (pin 24) is “L” level, IC becomes the standby mode. The power supply current is 10 µA (Max)
at the standby mode.
On/Off Setting Conditions
CTL
L
Power
OFF (Standby)
ON (Operating)
H
3. Protective Functions
(1) Timer-latch overcurrent protection circuit block (OCP)
The timer-latch overcurrent protection circuit is actuated upon completion of the soft-start period. When an
overcurrent flows, the circuit detects the increase in the voltage between the FET’s drain and source using the
external FET ON resistor, actuates the timer circuit, and starts charging the capacitor CSCP con-nected to the
CSCP terminal (pin 8). If the overcurrent remains flowing beyond the predetermined period of time, latch is set
and OUT terminlas (pin 3,22) of each channel are fixed at “H” level. And the circuit sets the latch to turn off the
external FET. The detection current value can be set by resistor RLIM1 connected between the FET’s drain and
the ILIM1 terminal (pin 5) and resistor RLIM2 connected between the drain and the ILIM2 terminal (pin 20).
Changing connection enables to detect overcurrent at current sense resistor.
To reset the actuated protection circuit, either the power supply turn off and on again or set the CTL terminal
(pin 6) to the “L” level to lower the VREF terminal (pin 17) voltage to 2.4 V (Min) or less. (See “1. Setting Timer-
Latch Overcurrent Protection Detection Current” in “■ABOUT TIMER-LATCH PROTECTION CIRCUIT”.)
(2) Timer-latch short-circuit protection circuit (SCP Logic, SCP Comp.)
The short-circuit detection comparator (SCP Comp.) detects the output voltage level of Error Amp, and if the
error amp output voltage of any channel falls below the short-circuit detection voltage (3.1 V Typ), the timer
circuits are actuated to start charging the external capacitor CSCP connected to the CSCP terminal (pin 8).
When the capacitor voltage reaches about 0.73 V, the circuit is turned off the output transistor and sets the dead
time to 100 %.
To reset the actuated protection circuit, either the power supply turn off and on again or set the CTL terminal
(pin 24) to the “L” level to lower the VREF terminal (pin 17) voltage to 2.4 V (Min) or less. (See “2. Setting Time
Constant for Timer-Latch Short-Circuit Protection Circuit” in “■ABOUT TIMER-LATCH PROTECTION CIR-
CUIT”.)
(3) Under voltage lockout protection circuit (UVLO)
The transient state or a momentary decrease in supply voltage, which occurs when the power supply is turned
on, may cause the IC to malfunction, resulting in breakdown or degradation of the system. To prevent such
malfunctions, undervoltagelockoutprotectioncircuitdetectsadecreaseininternalreferencevoltagewithrespect
to the power supply voltage, turns off the output transistor, and sets the dead time to 100% while holding the
CSCP terminal (pin 8) at the “L” level.
The circuit restores the output transistor to normal when the supply voltage reaches the threshold voltage of the
undervoltage lockout protection circuit.
(4) Protection circuit operating function table
This table refers to output condition when protection circuit is operating.
Operating circuit
Overcurrent protection circuit
Short-circuit protection circuit
Under-voltage lockout
CS1
CS2
OUT1
OUT2
L
L
L
L
L
L
H
H
H
H
H
H
12
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MB39A104
■ SETTING THE OUTPUT VOLTAGE
• Output Voltage Setting Circuit
VO
R1
(−INE2)
−INE1
15
10
Error Amp
−
+
+
1.24
R2
VO (V) =
(R1 + R2)
R2
1.24 V
(CS2)
CS1
14
11
■ SETTING THE TRIANGULAR OSCILLATION FREQUENCY
The triangular oscillation frequency is determined by the timing capacitor (CT) connected to the CT terminal (pin
13), and the timing resistor (RT) connected to the RT terminal (pin 12).
Moreover, it shifts more greatly than the caluculated values according to the constant of timing resistor (RT) when
the triangular wave oscillation frequency exceeds 1 MHz. Therefore, set it referring to “Triangular Wave Oscillation
Frequency vs. Timing Resistor” and “Triangular Wave Oscillation Frequency vs. Timing Capacitor” in “■TYPICAL
CHARACTERISTICS”.
Triangular oscillation frequency : fOSC
1200000
fOSC (kHz) =:
CT (pF) •RT (kΩ)
13
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MB39A104
■ SETTING THE SOFT-START AND DISCHARGE TIMES
To prevent rush currents when the IC is turned on, you can set a soft-start by connecting soft-start capacitors
(CS1 and CS2) to the CS1 terminal (pin 11) for channel 1 and the CS2 terminal (pin 14) for channel 2, respectively.
When CTL terminal (pin 24) goes to “H” level and IC starts (VCC ≥ UVLO threshold voltage), the external soft-
start capacitors (CS1 and CS2) connected to CS1 and CS2 terminals are charged at 10 µA. The error amplifier
output (FB1 (pin 9) , FB2 (pin 16) ) is determined by comparison between the lower one of the potentials at two
non-inverted input terminals (1.24 V, CS1 terminal voltages) and the inverted input terminal voltage (−INE1 (pin
10) voltage, −INE2 (pin 15) voltage).
The FB1 (FB2) terminal voltage is decided for the soft-start period by the comparison between 1.24 V in an
internal reference voltage and the voltages of the CS1 (CS2) terminal. The DC/DC converter output voltage
rises in proportion to the CS1 (CS2) terminal voltage as the soft-start capacitor connected to the CS1 (CS2)
terminal is charged.
The soft-start time is obtained from the following formula:
Soft-start time: ts (time to output 100%)
ts (s)=: 0.124 × CS (µF)
CS1 (CS2) terminal voltage
=: 5 V
Error Amp block −INE1 (−INE2) voltage
=: 1.24 V
=: 0 V
t
Soft-start time (ts)
14
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MB39A104
• Soft-Start Circuit
VREF
V
O
R1
R2
10 µA
−INE1
10
15
(−INE2)
L priority
Error Amp
−
CH ON/OFF signal
L : ON, H : OFF
+
+
11
14
CS1
(CS2)
CS1
1.24 V
(CS2)
FB1
9
16
(FB2)
UVLO
15
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MB39A104
■ TREATMENT WITHOUT USING CS TERMINAL
When not using the soft-start function, open the CS1 terminal (pin 11) and the CS2 terminal (pin 14) .
• Without Setting Soft-Start Time
“OPEN”
“OPEN”
14
CS2
11
CS1
16
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MB39A104
■ ABOUT TIMER-LATCH PROTECTION CIRCUIT
1. Setting Timer-Latch Overcurrent Protection Detection Current
The overcurrent protection circuit is actuated upon completion of the soft-start period. When an overcurrent
flows, the circuit detects the increase in the voltage between the FET’s drain and source using the external FET
ON resistor (RON), actuates the timer circuit, and starts charging the capacitor CSCP connected to the CSCP
terminal (pin 8). If the overcurrent remains flowing beyond the predetermined period of time, the circuit sets the
latch to fix OUT terminals (pin 3, 22) at “H” level and turn off the external FET. The detection current value can
be set by the resistors (RLIM1 and RLIM2) connected between the FET’s drain and the ILIM1 terminal (pin 5) and
between the drain and the ILIM2 terminal (pin 20), respectively.
The internal current (ILIM) can be set by the timing resistor (RT) connected to the RT terminal (pin 12).
Time until activating timer circuit and setting latch is equal to short-circuit detection time in "2. Setting Time
Constant for Timer-Latch Short-Circuit Protection Circuit".
Internal current value: ILIM
2700
ILIM (µA) =:
RT (kΩ)
Detection current value: IOCP
ILIM(A) × RLIM(Ω)
RON (Ω)
(VIN(V) − VO(V)) × VO(V)
2 × VIN(V) × fOSC(Hz) × L(H)
IOCP (A) =:
−
RLIM : Overcurrent detection resistor
RON : External FET ON resistor
VIN : Input voltage
VO : DC/DC converter output voltage
fOSC : Oscillation frequency
L
: Coil inductance
To reset the actuated protection circuit, either the power supply turn off and on again or set the CTL terminal
(pin 24) to the "L" level to lower the VREF terminal (pin 17) voltage to 2.4 V (Min) or less.
• Overcurrent detection circuit
VIN
Q1
L
(VS2)
VS1
21
4
VO
(ILIM2)
−
+
Current
Protection
Logic
20
ILIM1
(RLIM)
5
(1 µA)
Each
Channel
Drive
CSCP
8
VREF
UVLO
S
Latch
R
17
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MB39A104
Overcurrent Protection Circuit: Range of Operation
When an overcurrent flow occurs, if the increased voltage between the drain and source of the FET is detected
by means of the external FET (Q1) resistor, operational stability is lost when the external FET (Q1) ON interval
determined by the oscillation frequency, input voltage, and output voltage falls below 450 ns.
Therefore, the circuit should be used within a range that ensures that the ON interval does not fall below 450ns,
according to the following formula.
VO (V)
ON interval 450 (ns) ≥
VIN (V) × fOSC (Hz)
If the ON interval of the external FET (Q1) is below 450ns, we recommend the use of an overcurrent detection
resistor RS to detect overcurrent, as shown below.
This example shows the range of operation of the overcurrent detection function with a setting of Vo = 3.3V.
• Method to detect by current when external FET(Q1) is turned on
Overcurrent Detection Function Operating Range
1600
VIN
(Rs)
ErrAmp
Q1
1400
VO = set to 3.3 V
(VS2)
1200
1000
800
400
200
0
21
4
VS1
Operation Range
(ILIM2)
20
−
+
ILIM1
ConnecttoRS
when
5
using RS
6
8
10
12
14
16
18
20
VCC (V)
• Method to detect by mean current
Overcurrent Detection Function Operating Range
VIN
ErrAmp
1600
RS
Q1
1400
VO = set to 3.3 V
(VS2)
21
1200
VS1
4
1000
800
Operation Range
600
400
200
0
(ILIM2)
−
+
20
ILIM1
5
6
8
10
12
14
16
18
20
VCC (V)
18
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MB39A104
2. Setting Time Constant for Timer-Latch Short-Circuit Protection Circuit
Each channel uses the short-circuit detection comparator (SCP Comp.) to always compare the error amplifier′s
output level to the reference voltage (3.1 V Typ).
While DC/DC converter load conditions are stable on all channels, the short-circuit detection comparator output
remains at “L” level, and the CSCP terminal (pin 8) is held at “L” level.
If the load condition on a channel changes rapidly due to a short-circuit of the load, causing the output voltage
to drop, the output of the short-circuit detection comparator goes to “H” level. This causes the external short-
circuit protection capacitor CSCP connected to the CSCP terminal to be charged at 1 µA.
Short-circuit detection time (tSCP)
tSCP (s) =: 0.73 × CSCP (µF)
When the capacitor CSCP is charged to the threshold voltage (VTH =: 0.73 V), the latch is set and the external
FET is turned off (dead time is set to 100%). At this time, the latch input is closed and the CSCP terminal is
held at “L” level. If a short-circuit is detected on either of the two channels, both channels are shut off.
When the power supply is turned on back or VREF terminal (pin 17) voltage is less than 2.4 V (Min) by setting
CTL terminal (pin 24) to “L” level, the latch is released.
• Timer-latch short-circuit protection circuit
(FB2)
16
9
VO
FB1
R1
R2
(−INE2)
−INE1
15
10
Error
Amp
−
+
(1.24 V)
SCP
Comp.
+
+
−
(3.1 V)
(1 µA)
To each channel
Drive
CSCP
8
VREF
UVLO
S
R
Latch
19
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MB39A104
■ TREATMENT WITHOUT USING CSCP TERMINAL
When not using the timer-latch short-circuit protection circuit, connect the CSCP terminal (pin 8) to GND with
the shortest distance.
• Treatment without using CSCP
18
GND
8
CSCP
■ RESETTING THE LATCH OF EACH PROTECTION CIRCUIT
When the overcurrent, or short-circuit protection circuit detects each abnormality, it sets the latch to fix the output
at the "L" level.
To reset the actuated protection circuit, either the power supply turn off and on again or set the CTL terminal
(pin 24) to the "L" level to lower the VREF terminal (pin 17) voltage to 2.4 V (Min) or less.
20
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MB39A104
■ I/O EQUIVALENT CIRCUIT
⟨⟨Reference voltage block⟩⟩
⟨⟨Control block⟩⟩
⟨⟨Soft-start block⟩⟩
VREF
(5.0 V)
VCC
CSX
7
VCC
24
CTL
+
−
1.24 V
72
kΩ
VREF
17
77.8
kΩ
104
kΩ
24.8
kΩ
GND
GND
18
GND
⟨⟨Triangular wave oscillator
block (RT) ⟩⟩
⟨⟨Triangular wave oscillator
(CT) block⟩⟩
⟨⟨Short-circuit detection block⟩⟩
VCC
VREF
(5.0 V)
(3.1 V)
(3.1 V)
2 kΩ
+
−
1.35 V
CT
13
CSCP
8
RT
12
GND
VCC
GND
GND
⟨⟨Overcurrent protection circuit block⟩⟩
⟨⟨Error amplifier block (CH1, CH2) ⟩⟩
VCCO
VCC
ILIMX
VSX
VREF
(5.0 V)
−INEX
CSX
1.24 V
FBX
GND
GND
GNDO
⟨⟨PWM comparator
block (CH1, CH2) ⟩⟩
⟨⟨Bias voltage block⟩⟩
⟨⟨Output block (CH1, CH2) ⟩⟩
VCC
VCC
VCCO
VCCO
1
O
FBX
CT
VH
DTCX
2
VH
23
GNDO
GND
GND
GNDO
X : Each channel No.
21
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MB39A104
■ APPLICATION EXAMPLE
22
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MB39A104
■ PARTS LIST
COMPONENT
Q1, Q2
ITEM
Pch FET
Diode
SPECIFICATION
VDS = −30 V, ID = −6 A
VENDOR
TOSHIBA
ROHM
PARTS No.
TPC8102
D1, D2
VF = 0.42 V (Max) , at IF = 3 A
RB0530L-30
CDRH104R-150
L1, L2
Inductor
15 µH
3.6 A, 50 mΩ
SUMIDA
C1
Ceramics Condenser
OS-CONTM
100 pF
10 µF
10 µF
50 V
20 V
25 V
6.3 V
50 V
50 V
50 V
TDK
SANYO
TDK
C1608CH1H101J
20SVP10M
C2, C6
C3, C7
C4, C8
Ceramics Condenser
OS-CONTM
C3225JF1E106Z
6SVP82M
82 µF
SANYO
TDK
C10, C11, C20 Ceramics Condenser
C12, C14, C21 Ceramics Condenser
0.1 µF
1000 pF
0.1 µF
C1608JB1H104K
C1608JB1H102K
C1608JB1H104K
TDK
C16, C17
Ceramics Condenser
TDK
R1
R4, R5
R8, R13
R9, R14
R10
Resistor
Resistor
Resistor
Resistor
Resistor
Resistor
Resistor
Resistor
24 kΩ
2.7 kΩ
220 kΩ
68 kΩ
150 kΩ
56 kΩ
0.5 %
0.5 %
0.5 %
0.5 %
0.5 %
0.5 %
0.5 %
0.5 %
ssm
ssm
ssm
ssm
ssm
ssm
ssm
ssm
RR0816P-243-D
RR0816P-272-D
RR0816P-224-D
RR0816P-683-D
RR0816P-154-D
RR0816P-563-D
RR0816P-104-D
RR0816P-133-D
R11
R15
100 kΩ
13 kΩ
R16
Note : TOSHIBA : TOSHIBA Corporation
ROHM : ROHM Co., Ltd
SANYO : SANYO Electric Co., Ltd.
TDK
SUMIDA : SUMIDA Electric Co., Ltd.
ssm : SUSUMU Co., Ltd.
: TDK Corporation
23
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MB39A104
■ SELECTION OF COMPONENTS
• Pch MOS FET
The P-ch MOSFET for switching use should be rated for at least 20% more than the maximum input voltage. To
minimize continuity loss, use a FET with low RDS(ON) between the drain and source. For high input voltage and
high frequency operation, on/off-cycle switching loss will be higher so that power dissipation must be considered.
In this application, the Toshiba TPC8102 is used. Continuity loss, on/off switching loss, and total loss are deter-
mined by the following formulas. The selection must ensure that peak drain current does not exceed rated values,
and also must be in accordance with overcurrent detection levels.
Continuity loss : PC
2
PC = ID × RDS (ON) × Duty
On-cycle switching loss : PS (ON)
VD (Max) × ID × tr × fOSC
PS (ON) =
6
Off-cycle switching loss : PS (OFF)
VD (Max) × ID (Max) × tf × fOSC
PS (OFF) =
6
Total loss : PT
PT = PC + PS (ON) + PS (OFF)
Example: Using the Toshiba TPC8102
CH1
Input voltage VIN (Max) = 19 V, output voltage VO = 5 V, drain current ID = 3 A, Oscillation frequency fOSC = 500 kHz,
L = 15 µH, drain-source on resistance RDS (ON) =: 50 mΩ, tr = tf=: 100 ns.
Drain current (Max) : ID (Max)
VIN − VO
ID (Max) = IO +
ton
2L
19 − 5
1
= 3 +
×
×
× 0.263
2 × 15 × 10−6
500 × 103
=: 3.25 (A)
Drain current (Min) : ID (Min)
VIN − VO
ID (Min) = IO −
ton
2L
19 − 5
2 × 15 × 10−6
1
= 3 −
× 0.263
500 × 103
=: 2.75 (A)
24
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MB39A104
2
PC = ID × RDS (ON) × Duty
= 3 2 × 0.05 × 0.263
=: 0.118 W
VD (Max) × ID × tr × fOSC
PS (ON)
=
=
6
19 × 3 × 100 × 10−9 × 500 × 103
6
=: 0.475 W
VD (Max) × ID (Max) × tf × fOSC
PS (OFF)
=
6
19 × 3.25 × 100 × 10−9 × 500 × 103
=
6
=: 0.515 W
PT
= PC + PS (ON) + PS (OFF)
=: 0.118 + 0.475 + 0.515
=: 1.108 W
The above power dissipation figures for the TPC8102 are satisfied with ample margin at 2.4 W (Ta = +25 °C) .
CH2
Input voltage VIN (Max) = 19 V output voltage VO = 3.3 V, drain current ID = 3 A, Oscillation frequency
fOSC = 500 kHz, L = 15 µH, drain-source on resistance RDS (ON) =: 50 mΩ, tr = tf=: 100 ns.
Drain current (Max) : ID (Max)
VIN − VO
ID (Max) = IO +
ton
2L
19 − 3.3
1
= 3 +
×
×
× 0.174
2 × 15 × 10−6
500 × 103
=: 3.18 (A)
Drain current (Min) : ID (Min)
VIN − VO
ID (Min) = IO −
ton
2L
19 − 3.3
1
= 3 −
× 0.174
2 × 15 × 10−6
500 × 103
=: 2.82 (A)
25
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MB39A104
2
PC = ID × RDS (ON) × Duty
=
3 2 × 0.05 × 0.174
=: 0.078 W
VD (Max) × ID × tr × fOSC
PS (ON)
=
=
6
19 × 3 × 100 × 10−9 × 500 × 103
6
=: 0.475 W
VD (Max) × ID (Max) × tf × fOSC
PS (OFF)
=
=
6
19 × 3.18 × 100 × 10−9 × 500 × 103
6
=: 0.504 W
PT = PC + PS (ON) + PS (OFF)
=: 0.078 + 0.475 + 0.504
=: 1.057 W
The above power dissipation figures for the TPC8102 are satisfied with ample margin at 2.4 W (Ta = +25 °C) .
• Inductors
In selecting inductors, it is of course essential not to apply more current than the rated capacity of the inductor,
but also to note that the lower limit for ripple current is a critical point that if reached will cause discontinuous
operation and a considerable drop in efficiency. This can be prevented by choosing a higher inductance value,
which will enable continuous operation under light loads. Note that if the inductance value is too high, however,
direct current resistance (DCR) is increased and this will also reduce efficiency. The inductance must be set at
the point where efficiency is greatest.
Note also that the DC superimposition characteristics become worse as the load current value approaches the
rated current value of the inductor, so that the inductance value is reduced and ripple current increases, causing
loss of efficiency. The selection of rated current value and inductance value will vary depending on where the
point of peak efficiency lies with respect to load current.
Inductance values are determined by the following formulas.
The L value for all load current conditions is set so that the peak to peak value of the ripple current is 1/2 the
load current or less.
Inductance value : L
2 (VIN − VO)
L ≥
ton
IO
26
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MB39A104
Example:
CH1
2 (VIN − VO)
L ≥
ton
IO
2 × (19 − 5)
1
≥
×
× 0.263
IO
500 × 103
≥ 4.91 µH
CH2
2 (VIN − VO)
L ≥
ton
IO
2 × (19 − 3.3)
1
≥
×
× 0.174
IO
500 × 103
≥ 3.64 µH
Inductance values derived from the above formulas are values that provide sufficient margin for continuous
operation at maximum load current, but at which continuous operation is not possible at light loads. It is therefore
necessary to determine the load level at which continuous operation becomes possible. In this application, the
Sumida CDRH104R-150 is used. At 15 µH, the load current value under continuous operating conditions is
determined by the following formula.
Load current value under continuous operating conditions : IO
VO
2L
IO ≥
toff
Example: Using the CDRH104R-150
15 µH (allowable tolerance ±30%) , rated current = 3.6 A
CH1
VO
2L
IO ≥
toff
5
1
≥
×
× (1 − 0.263)
2 × 15 × 10−6
500 × 103
≥ 245.7 mA
CH2
VO
toff
2L
IO
≥
3.3
1
≥
× (1 − 0.174)
2 × 15 × 10−6 × 500 × 103
≥ 181.7 mA
27
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MB39A104
To determine whether the current through the inductor is within rated values, it is necessary to determine the
peak value of the ripple current as well as the peak-to-peak values of the ripple current that affect the output
ripple voltage. The peak value and peak-to-peak value of the ripple current can be determined by the following
formulas.
Peak value : IL
VIN − VO
IL ≥ IO +
ton
2L
Peak-to-peak value : ∆IL
VIN − VO
∆IL =
ton
L
Example: Using the CDRH104R-150
15 µH (allowable tolerance ±30%) , rated current = 3.6 A
Peak value:
CH1
VIN − VO
ton
IL ≥ IO +
2L
19 − 5
1
× 0.263
≥ 3 +
2 × 15 × 10−6 × 500 × 103
≥ 3.25 A
CH2
VIN − VO
IL ≥ IO +
ton
2L
19 − 3.3
1
≥ 3 +
×
× 0.174
2 × 15 × 10−6
500 × 103
≥ 3.18 A
Peak-to-peak value:
CH1
VIN − VO
∆IL =
ton
L
19 − 5
1
=
× 0.263
15 × 10−6 × 500 × 103
= 0.491 A
CH2
VIN − VO
∆IL =
ton
L
19 − 3.3
1
=
×
× 0.174
15 × 10−6
500 × 103
= 0.364 A
28
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MB39A104
• Flyback diode
The flyback diode is generally used as a Shottky barrier diode (SBD) when the reverse voltage to the diode is
less than 40V. The SBD has the characteristics of higher speed in terms of faster reverse recovery time, and
lower forward voltage, and is ideal for achieving high efficiency. As long as the DC reverse voltage is sufficiently
higher than the input voltage, the average current flowing through the diode is within the average output current
level, and peak current is within peak surge current limits, there is no problem. In this application the Rohm
RB053L-30 is used. The diode average current and diode peak current can be calculated by the following
formulas.
Diode mean current : IDi
VO
VIN
IDi ≥ IO × (1 −
)
Diode peak current : IDip
VO
IDip ≥ (IO +
toff)
2L
Example: Using the Rohm RB053L-30
VR (DC reverse voltage) = 30 V, average output voltage = 3.0 A, peak surge current = 70 A,
VF (forward voltage) = 0.42 V, IF = 3.0 A
CH1
IDi ≥ IO × (1 −
VO
VIN
)
≥ 3 × (1 − 0.263)
≥ 2.21 A
CH2
IDi ≥ IO × (1 −
VO
VIN
)
≥ 3 × (1 − 0.174)
≥ 2.48 A
CH1
VO
2L
IDip ≥ (IO +
toff)
toff)
≥ 3.24 A
CH2
VO
2L
IDip ≥ (IO +
≥ 3.18 A
29
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MB39A104
• Smoothing Capacitor
The smoothing capacitor is an indispensable element for reducing ripple voltage in output. In selecting a smooth-
ing capacitor it is essential to consider equivalent series resistance (ESR) and allowable ripple current. Higher
ESR means higher ripple voltage, so that to reduce ripple voltage it is necessary to select a capacitor with low
ESR. However, the use of a capacitor with low ESR can have substantial effects on loop phase characteristics,
and therefore requires attention to system stability. Care should also be taken to use a capacity with sufficient
margin for allowable ripple current. This application uses the (OS-CON TM) 6SVP82M made by Sanyo. The ESR,
capacitance value, and ripple current can be calculated from the following formulas.
Equivalent Series Resistance : ESR
∆VO
∆IL
1
ESR ≤
−
2πfCL
Capacitance value : CL
∆IL
CL
≥ 2πf (∆VO − ∆IL × ESR)
Ripple current : ICLrms
(VIN − VO) ton
ICLrms ≥
2√3L
Example: Using the 6SVP82M
Rated voltage = 6.3 V, ESR = 50 mΩ, maximum allowable ripple current = 1570 mArms
Equivalent series resistance
CH1
∆VO
∆IL
1
ESR ≤
−
2πfCL
0.050
0.491
1
≤
−
2π × 500 × 103 × 82 × 10−6
≤ 98.0 mΩ
30
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MB39A104
CH2
ESR
∆VO
∆IL
0.033
0.364
1
≤
≤
−
2πfCL
1
−
2π × 500 × 103 × 82 × 10−6
≤ 86.8 mΩ
Capacitance value
CH1
∆IL
CL
≥
2πf (∆VO − ∆IL × ESR)
0.491
≥
2π × 500 × 103 × (0.050 − 0.491 × 0.05)
≥ 6.14 µF
CH2
∆IL
CL ≥
2πf (∆VO − ∆IL × ESR)
0.364
2π × 500 × 103 × (0.033 − 0.364 × 0.05)
≥
≥ 7.83 µF
Ripple current
CH1
(VIN − VO) ton
2√3L
(19 − 5) × 0.263
2√3 × 15 × 10−6 × 500 × 103
ICLrms ≥
≥
≥ 141.7 mArms
CH2
(VIN − VO) ton
ICLrms ≥
2√3L
(19 − 3.3) × 0.174
2√3 × 15 × 10−6 × 500 × 103
≥
≥ 105.1 mArms
31
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MB39A104
■ REFERENCE DATA
TOTAL Efficiency vs. Input Voltage
100
90
80
70
60
50
40
Vin = 7 V
Vin = 10 V
Vin = 12 V
Vin = 19 V
Ta = +25 °C
5 V Output
SW1 = OFF
SW2 = ON
30
10 m
100 m
1
10
Input voltage VIN (V)
Each CH Efficiency vs. Input Voltage
100
90
80
70
60
50
40
Vin = 7 V
Vin = 10 V
Vin = 12 V
Vin = 19 V
Ta = +25 °C
3.3 V Output
SW1 = ON
SW2 = OFF
30
10 m
100 m
1
10
Input voltage VIN (V)
(Continued)
32
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MB39A104
(Continued)
Switching Wave Form (CH1)
VG (V)
Ta = +25 °C
VIN = 12 V
CTL = 5 V
VO = 5 V
15
10
5
RL = 1.67 Ω
0
VS (V)
15
10
5
0
0
1
2
3
4
5
6
7
8
9
10
t (µs)
Switching Wave Form (CH2)
VG (V)
Ta = +25 °C
VIN = 12 V
CTL = 5 V
VO = 3.3 V
RL = 1.1 Ω
15
10
5
0
VS (V)
15
10
5
0
0
1
2
3
4
5
6
7
8
9
10
t (µs)
33
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MB39A104
■ USAGE PRECAUTION
• Printed circuit board ground lines should be set up with consideration for common impedance.
• Take appropriate static electricity measures.
• Containers for semiconductor materials should have anti-static protection or be made of conductive material.
• After mounting, printed circuit boards should be stored and shipped in conductive bags or containers.
• Work platforms, tools, and instruments should be properly grounded.
• Working personnel should be grounded with resistance of 250 kΩ to 1 MΩ between body and ground.
• Do not apply negative voltages.
The use of negative voltages below –0.3 V may create parasitic transistors on LSI lines, which can cause
abnormal operation.
■ ORDERING INFORMATION
Part number
Package
Remarks
24-pin plastic SSOP
(FPT-24P-M03)
MB39A104PFV
34
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MB39A104
■ PACKAGE DIMENSIONS
Note 1) *1 : Resin protrusion. (Each side : +0.15 (.006) MAX) .
Note 2) *2 : These dimensions do not include resin protrusion.
Note 3) Pins width and pins thickness include plating thickness.
Note 4) Pins width do not include tie bar cutting remainder.
24-pin plastic SSOP
(FPT-24P-M03)
1
0.17±0.03
(.007±.001)
*
7.75±0.10(.305±.004)
24
13
*25.60±0.10 7.60±0.20
(.220±.004) (.299±.008)
INDEX
Details of "A" part
1.25 +0.20
–0.10
–.004
(Mounting height)
.049 +.008
0.25(.010)
0~8˚
"A"
1
12
0.24 +0.08
.009 +.003
–0.07
0.65(.026)
M
0.13(.005)
–.003
0.50±0.20
0.10±0.10
(.020±.008)
(.004±.004)
(Stand off)
0.60±0.15
(.024±.006)
0.10(.004)
C
2003 FUJITSU LIMITED F24018S-c-4-5
Dimensions in mm (inches)
Note : The values in parentheses are reference values.
35
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